参数资料
| 型号： | AD8062ARMZ-RL |
| 厂商： | Analog Devices Inc |
| 文件页数： | 6/20页 |
| 文件大小： | 0K |
| 描述： | IC OPAMP VF R-R DUAL LP 8MSOP |
| 标准包装： | 3,000 |
| 放大器类型： | 电压反馈 |
| 电路数： | 2 |
| 输出类型： | 满摆幅 |
| 转换速率： | 650 V/µs |
| -3db带宽： | 320MHz |
| 电流 - 输入偏压： | 3.5µA |
| 电压 - 输入偏移： | 1000µV |
| 电流 - 电源： | 6.8mA |
| 电流 - 输出 / 通道： | 50mA |
| 电压 - 电源，单路/双路(±)： | 2.7 V ~ 8 V，±1.35 V ~ 4 V |
| 工作温度： | -40°C ~ 85°C |
| 安装类型： | 表面贴装 |
| 封装/外壳： | 8-TSSOP，8-MSOP（0.118"，3.00mm 宽） |
| 供应商设备封装： | 8-MSOP |
| 包装： | 带卷 (TR) |
AD8061/AD8062/AD8063
Data Sheet
Rev. J | Page 14 of 20
CIRCUIT DESCRIPTION
The AD8061/AD8062/AD8063 family is comprised of high
speed voltage feedback op amps. The high slew rate input stage
is a true, single-supply topology, capable of sensing signals at or
below the minus supply rail. The rail-to-rail output stage can
pull within 30 mV of either supply rail when driving light loads
and within 0.3 V when driving 150 . High speed perform-
ance is maintained at supply voltages as low as 2.7 V.
HEADROOM CONSIDERATIONS
These amplifiers are designed for use in low voltage systems.
To obtain optimum performance, it is useful to understand the
behavior of the amplifier as input and output signals approach
the amplifier’s headroom limits.
The AD8061/AD8062/AD8063 input common-mode voltage
range extends from the negative supply voltage (actually 200 mV
below this), or ground for single-supply operation, to within
1.8 V of the positive supply voltage. Thus, at a gain of 2, the
AD8061/AD8062/AD8063 can provide full rail-to-rail output
swing for supply voltage as low as 3.6 V, assuming the input
signal swings from VS (or ground) to +VS/2. At a gain of 3,
the AD8061/AD8062/AD8063 can provide a rail-to-rail output
range down to 2.7 V total supply voltage.
Exceeding the headroom limit is not a concern for any inverting
gain on any supply voltage, as long as the reference voltage at
the amplifier’s positive input lies within the amplifier’s input
common-mode range.
The input stage is the headroom limit for signals when the
amplifier is used in a gain of 1 for signals approaching the
positive rail. Figure 45 shows a typical offset voltage vs. input
common-mode voltage for the AD8061/AD8062/AD8063
amplifier on a 5 V supply. Accurate dc performance is main-
tained from approximately 200 mV below the minus supply
to within 1.8 V of the positive supply. For high speed signals,
however, there are other considerations. Figure 46 shows 3 dB
bandwidth vs. dc input voltage for a unity-gain follower. As
the common-mode voltage approaches the positive supply,
the amplifier holds together well, but the bandwidth begins to
drop at 1.9 V within +VS.
This manifests itself in increased distortion or settling time.
Figure 16 plots the distortion of a 1 V p-p signal with the
AD8061/AD8062/AD8063 amplifier used as a follower on
a 5 V supply vs. signal common-mode voltage. Distortion
performance is maintained until the input signal center voltage
gets beyond 2.5 V, as the peak of the input sine wave begins to
run into the upper common-mode voltage limit.
VCM (V)
V
OS
(m
V)
–4.0
–3.6
–3.2
–2.8
–2.4
–2.0
–1.6
–1.2
–0.8
–0.4
–0.5
0
0.5
1.0
1.5
2.0
2.5
3.0
3.5
4.0
01065-
045
Figure 45. VOS vs. Common-Mode Voltage, VS = 5 V
FREQUENCY (MHz)
2
–8
0.1
G
AI
N
(
d
B)
–4
0
–2
–6
1
10
100
1k
10k
01065-
046
VCM = 3.0
VCM = 3.1
VCM = 3.2
VCM = 3.3
VCM = 3.4
Figure 46. Unity-Gain Follower Bandwidth vs. Input Common Mode, VS = 5 V
Higher frequency signals require more headroom than lower
frequencies to maintain distortion performance. Figure 47
illustrates how the rising edge settling time for the amplifier
configured as a unity-gain follower stretches out as the top of
a 1 V step input approaches and exceeds the specified input
common-mode voltage limit.
For signals approaching the minus supply and inverting gain
and high positive gain configurations, the headroom limit is
the output stage. The AD8061/AD8062/AD8063 amplifiers use
a common emitter style output stage. This output stage
maximizes the available output range, limited by the saturation
voltage of the output transistors. The saturation voltage
increases with the drive current the output transistor is required
to supply, due to the output transistors’ collector resistance. The
saturation voltage is estimated using the equation
VSAT = 25 mV + IO × 8
where:
IO is the output current.
8 is a typical value for the output transistors’ collector
resistance.
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