AD8344
Rev. 0 | Page 16 of 20
0
–50
–45
–40
–35
–30
–25
–20
–15
–10
–5
0.1
1
10
0
FREQUENCY (GHz)
R
IDEAL LPF
REAL LPF
4.7pF
4.7pF
6.8nH
Figure 43. Measured and Ideal LO Filter Frequency Response
BIAS RESISTOR SELECTION
An external bias resistor is used to set the dc current in the
mixer core. This provides the ability to reduce power consump-
tion at the expense of decreased dynamic range. Figure 44
shows the spurious-free dynamic range (SFDR) of the mixer for
a 1 Hz noise bandwidth versus the R
BIAS
resistor value. SFDR
was calculated using NF and IIP3 data collected at 900 MHz.
By definition,
(
)
)
B
(
10log
3
2
kT
NF
IIP3
SFDR
=
where
IIP3
is the input third-order intercept in dBm.
NF
is the
noise figure in dB.
kT
is the thermal noise power density and is
173.86 dBm/Hz at 298°K.
B
is the noise bandwidth in Hz.
In order to calculate the anticipated SFDR for a given applica-
tion, it is necessary to factor in the actual noise bandwidth. For
instance, if the IF noise bandwidth was 5 MHz, the anticipated
SFDR using a 2.43 k R
BIAS
would be 6.66 log10 (5 MHz) less
than the 1 Hz data in Figure 44 or ~80 dBc. Using a 2.43 k bias
resistor will set the quiescent power dissipation to ~415 mW for
a 5 V supply. If the R
BIAS
resistor value was raised to 3.9 k, the
SFDR for the same 5 MHz bandwidth would be reduced to
~77.5 dBc and the power dissipation would be reduced to
~335 mW In low power portable applications it may be advanta-
geous to reduce power consumption by using a larger value of R
BIAS
,
assuming reduced dynamic range performance is acceptable.
125
120
85
81
77
73
69
65
121
122
123
124
2.4
2.6
2.8
3.0
3.2
3.4
3.6
3.8
4.0
0
R
BIAS
(k
)
S
S
AD8344
COMM
9
EXRB
10
PWDN
11
VPDC
12
+V
S
R
BIAS
Figure 44. Impact of R
BIAS
Resistor Selection vs. Spurious-Free
Dynamic Range and Power Consumption,
F
RF
= 890 MHz and F
LO
= 1090 MHz
CONVERSION GAIN AND IF LOADING
The AD8344 is optimized for driving a 200 differential load.
Although the device is capable of driving a wide variety of
loads, in order to maintain optimum distortion and noise
performance, it is advised that the presented load at the IF
outputs is reasonably close to 200 . Figure 45 illustrates the
effect of IF loading on conversion gain. The mixer outputs
behave like Norton equivalent sources, where the conversion
gain is the effective transconductance of the mixer multiplied
by the loading impedance. The linear differential voltage
conversion gain of the mixer can be modeled as
RF
m
m
37.70
LOAD
f
g
j
g
×
R
Av
×
×
+
×
×
=
1
0.46
where
R
LOAD
is the differential loading impedance.
g
m
is the
mixer transconductance and is equal to 4070/R
BIAS
.
f
RF
is the
frequency of the signal applied to the RF port in GHz.
Large impedance loads cause the conversion gain to increase,
resulting in a decrease in input linearity and allowable signal
swing. In order to maintain positive conversion gain and pre-
serve spurious-free dynamic range performance, the differential
load presented at the IF port should remain within a range of
~100 to 250 .