参数资料
| 型号： | EL5176IYZ-T7 |
| 厂商： | Intersil |
| 文件页数： | 2/12页 |
| 文件大小： | 0K |
| 描述： | IC DRVR TWIST 250MHZ SGL 10-MSOP |
| 标准包装： | 1 |
| 放大器类型： | 差分 |
| 电路数： | 1 |
| 输出类型： | 差分 |
| 转换速率： | 800 V/µs |
| 增益带宽积： | 100MHz |
| -3db带宽： | 250MHz |
| 电流 - 输入偏压： | 6µA |
| 电压 - 输入偏移： | 1500µV |
| 电流 - 电源： | 7.5mA |
| 电流 - 输出 / 通道： | 50mA |
| 电压 - 电源，单路/双路(±)： | 4.75 V ~ 11 V，±2.38 V ~ 5.5 V |
| 工作温度： | -40°C ~ 85°C |
| 安装类型： | 表面贴装 |
| 封装/外壳： | 10-TFSOP，10-MSOP（0.118"，3.00mm 宽） |
| 供应商设备封装： | 10-MSOP |
| 包装： | 标准包装 |
| 其它名称： | EL5176IYZ-T7DKR |
EL5176
10
FN7343.5
August 28, 2012
The bandwidth of the EL5176 depends on the load and the
feedback network. RF and RG appear in parallel with the load for
gains other than +1. As this combination gets smaller, the
bandwidth falls off. Consequently, RF also has a minimum value
that should not be exceeded for optimum bandwidth
performance. For gain of +1, RF = 0 is optimum. For the gains
other than +1, optimum response is obtained with RF between
500 to 1k.
The EL5176 has a gain bandwidth product of 100MHz for
RLD =1k. For gains ≥5, its bandwidth can be predicted by
Equation 2:
Driving Capacitive Loads and Cables
The EL5176 can drive a 50pF differential capacitor in parallel with
1k differential load with less than 5dB of peaking at a gain of +1.
If less peaking is desired in applications, a small series resistor
(usually between 5 to 50) can be placed in series with each
output to eliminate most peaking. However, this will reduce the
gain slightly. If the gain setting is greater than 1, the gain resistor
RG can then be chosen to make up for any gain loss, which may be
created by the additional series resistor at the output.
When used as a cable driver, double termination is always
recommended for reflection-free performance. For those
applications, a back-termination series resistor at the amplifier's
output will isolate the amplifier from the cable and allow
extensive capacitive drive. However, other applications may have
high capacitive loads without a back-termination resistor. Again,
a small series resistor at the output can help to reduce peaking.
Disable/Power-Down
The EL5176 can be disabled and its outputs placed in a high
impedance state. The turn-off time is about 0.95s and the turn-
on time is about 215ns. When disabled, the amplifier's supply
current is reduced to 1.7A for IS+ and 120A for IS- typically,
thereby effectively eliminating the power consumption. The
amplifier's power-down can be controlled by standard CMOS
signal levels at the ENABLE pin. The applied logic signal is
relative to VS+ pin. Letting the EN pin float or applying a signal
that is less than 1.5V below VS+ will enable the amplifier. The
amplifier will be disabled when the signal at the EN pin is above
VS+ - 0.5V.
Output Drive Capability
The EL5176 has internal short circuit protection. Its typical short
circuit current is ±40mA for EL5176. If the output is shorted
indefinitely, the power dissipation could easily increase such that
the part will be destroyed. Maximum reliability is maintained if
the output current never exceeds ±40mA. This limit is set by the
design of the internal metal interconnect.
Power Dissipation
With the high output drive capability of the EL5176, it is possible
to exceed the +135°C absolute maximum junction temperature
under certain load current conditions. Therefore, it is important
to calculate the maximum junction temperature for the
application to determine if the load conditions or package types
need to be modified for the amplifier to remain in the safe
operating area.
The maximum power dissipation allowed in a package is
determined according to Equation 3:
Where:
TJMAX = Maximum junction temperature
TAMAX = Maximum ambient temperature
θJA = Thermal resistance of the package
The maximum power dissipation actually produced by an IC is
the total quiescent supply current times the total power supply
voltage, plus the power in the IC due to the load, or as expressed
in Equation 4:
Where:
VSTOT = Total supply voltage = VS+ - VS-
ISMAX = Maximum quiescent supply current per channel
ΔVO = Maximum differential output voltage of the application
RLD = Differential load resistance
ILOAD = Load current
i = Number of channels
By setting the two PDMAX equations equal to each other, we can
solve the output current and RLD to avoid the device overheat.
Power Supply Bypassing and Printed Circuit
Board Layout
As with any high frequency device, a good printed circuit board
layout is necessary for optimum performance. Lead lengths
should be as short as possible. The power supply pin must be
well bypassed to reduce the risk of oscillation. For normal single
supply operation, where the VS- pin is connected to the ground
plane, a single 4.7F tantalum capacitor in parallel with a 0.1F
ceramic capacitor from VS+ to GND will suffice. This same
capacitor combination should be placed at each supply pin to
ground if split supplies are to be used. In this case, the VS- pin
becomes the negative supply rail.
For good AC performance, parasitic capacitance should be kept
to a minimum. Use of wire-wound resistors should be avoided
because of their additional series inductance. Use of sockets
should also be avoided if possible. Sockets add parasitic
inductance and capacitance that can result in compromised
performance. Minimizing parasitic capacitance at the amplifier's
inverting input pin is very important. The feedback resistor
should be placed very close to the inverting input pin. Strip line
design techniques are recommended for the signal traces.
As the signal is transmitted through a cable, the high frequency
signal will be attenuated. One way to compensate this loss is to
boost the high frequency gain at the receiver side.
Gain
BW
100MHz
=
×
(EQ. 2)
PD
MAX
T
JMAX
T
AMAX
–
Θ
JA
---------------------------------------------
=
(EQ. 3)
(EQ. 4)
PD
i
V
STOT
I
SMAX
×
V
(
STOT
ΔV
O )
–
ΔV
O
R
LD
------------
×
+
×
=
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