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参数资料
| 型号： | FSL106MR |
| 厂商： | FAIRCHILD SEMICONDUCTOR CORP |
| 元件分类： | 稳压器 |
| 英文描述： | 0.62 A SWITCHING CONTROLLER, 73 kHz SWITCHING FREQ-MAX, PDIP8 |
| 封装： | ROHS COMPLIANT, MS-001BA, DIP-8 |
| 文件页数： | 13/13页 |
| 文件大小： | 932K |
| 代理商： | FSL106MR |
2010 Fairchild Semiconductor Corporation
www.fairchildsemi.com
FSL106MR Rev. 1.0.2
9
FSL106M
R
—
Green
M
ode
Fairchild
Power
Swit
ch
(
F
PS)
Functional Description
Startup
At startup, an internal high-voltage current source
supplies the internal bias and charges the external
capacitor (CA) connected with the VCC pin, as illustrated
in Figure 14. When VCC reaches the start voltage of
12V, the FPS begins switching and the internal high-
voltage current source is disabled. The FPS continues
normal switching operation and the power is provided
from the auxiliary transformer winding unless VCC goes
below the stop voltage of 8V.
Figure 14. Startup Circuit
Oscillator Block
The oscillator frequency is set internally and the FPS
has a random frequency fluctuation function.
Fluctuation of the switching frequency of a switched
power supply can reduce EMI by spreading the energy
over a wider frequency range than the bandwidth
measured by the EMI test equipment. The amount of
EMI reduction is directly related to the range of the
frequency variation. The range of frequency variation is
fixed internally; however, its selection is randomly
chosen by the combination of external feedback voltage
and internal free-running oscillator. This randomly
chosen switching frequency effectively spreads the EMI
noise nearby switching frequency and allows the use of
a cost-effective inductor instead of an AC input line filter
to satisfy the world-wide EMI requirements.
Figure 15. Frequency Fluctuation Waveform
Feedback Control
FSL106MR employs current-mode control, as shown in
Figure 16. An opto-coupler (such as the FOD817A) and
shunt regulator (such as the KA431) are typically used
to implement the feedback network. Comparing the
feedback voltage with the voltage across the RSENSE
resistor makes it possible to control the switching duty
cycle. When the shunt regulator reference pin voltage
exceeds the internal reference voltage of 2.5V, the
opto-coupler LED current increases, the feedback
voltage VFB is pulled down, and the duty cycle is
reduced. This typically occurs when the input voltage is
increased or the output load is decreased.
Figure 16. Pulse-Width-Modulation Circuit
Leading-Edge Blanking (LEB)
At the instant the internal SenseFET is turned on, the
primary-side capacitance and secondary-side rectifier
diode reverse recovery typically cause a high-current
spike through the SenseFET. Excessive voltage across
the RSENSE resistor leads to incorrect feedback
operation in the current-mode PWM control. To counter
this effect, the FPS employs a leading-edge blanking
(LEB) circuit (see the Figure 16). This circuit inhibits the
PWM comparator for a short time (tLEB) after the
SenseFET is turned on.
Protection Circuits
The FPS has several protective functions, such as
overload protection (OLP), over-voltage protection
(OVP), output short-circuit protection (OSP), under-
voltage
lockout
(UVLO),
abnormal
over-current
protection (AOCP), and thermal shutdown (TSD).
Because these various protection circuits are fully
integrated inside the IC without external components,
reliability is improved without increasing cost. Once a
fault condition occurs, switching is terminated and the
SenseFET remains off. This causes VCC to fall. When
VCC reaches the UVLO stop voltage VSTOP (8V), the
protection is reset and the internal high-voltage current
source charges the VCC capacitor via the VSTR pin.
When VCC reaches the UVLO start voltage VSTART
(12V), the FPS resumes normal operation. In this
manner, the auto-restart can alternately enable and
disable the switching of the power SenseFET until the
fault condition is eliminated.
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