参数资料
型号: G1422
厂商: Global Mixed-mode Technology Inc.
元件分类: 音频放大器
英文描述: 2W Stereo Audio Amplifier
中文描述: 2W立体声音频放大器
文件页数: 5/15页
文件大小: 304K
代理商: G1422
Ver: 1.2
Jun 29, 2005
TEL: 886-3-5788833
http://www.gmt.com.tw
13
G1422
Global Mixed-mode Technology Inc.
Application Information
Single Ended Mode Operation
The G1422 can drive clean, low distortion SE output
power into headphone loads (generally 16
Ω or 32Ω)
as in Figure A. Please refer to Electrical Characteris-
tics
to see the performances. A coupling capacitor is
needed to block the dc offset voltage, allowing pure ac
signals into headphone loads. Choosing the coupling
capacitor will also determine the 3 dB point of the
high-pass filter network, as Figure B.
fC=1/(2πRLCC)
For example, a 68uF capacitor with 32
Ω headphone
load would attenuate low frequency performance be-
low 73Hz. So the coupling capacitor should be well
chosen to achieve the excellent bass performance
when in SE mode operation.
Bridged-Tied Load Mode Operation
The G1422 has two linear amplifiers to drive both ends
of the speaker load in Bridged-Tied Load (BTL) mode
operation. Figure C shows the BTL configuration. The
differential driving to the speaker load means that
when one side is slewing up, the other side is slewing
down, and vice versa. This configuration in effect will
double the voltage swing on the load as compared to a
ground reference load. In BTL mode, the peak-to-peak
voltage VO(PP) on the load will be two times than a
ground reference configuration. The voltage on the
load is doubled, this will also yield 4 times output
power on the load at the same power supply rail and
loading. Another benefit of using differential driving
configuration is that BTL operation cancels the dc off-
sets, which eliminates the dc coupling capacitor that is
needed to cancelled dc offsets in the ground reference
configuration. Low-frequency performance is then lim-
ited only by the input network and speaker responses.
Cost and PCB space can be minimized by eliminating
the dc coupling capacitors.
VDD
Vo(PP)
CC
RL
Figure A
VDD
Vo(PP)
CC
RL
Figure A
-3 dB
fc
Figure B
-3 dB
fc
Figure B
VDD
Vo(PP)
VDD
-Vo(PP)
2xVo(PP)
RL
Figure C
VDD
Vo(PP)
VDD
-Vo(PP)
2xVo(PP)
RL
Figure C
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