参数资料
型号: IR3622AMPBF
厂商: International Rectifier
文件页数: 21/33页
文件大小: 0K
描述: IC REG CTRLR BUCK PWM VM 32MLPQ
标准包装: 73
PWM 型: 电压模式
输出数: 2
频率 - 最大: 600kHz
占空比: 84%
电源电压: 4.5 V ~ 14.5 V
降压:
升压:
回扫:
反相:
倍增器:
除法器:
Cuk:
隔离:
工作温度: -40°C ~ 125°C
封装/外壳: 32-VFQFN 裸露焊盘
包装: 管件
配用: IRDC3622S-ND - BOARD EVALUATION W/IR3622MPBF
IRDC3622D-ND - BOARD EVAL W/IR3622MPBF DUAL OUT
IR3622AMPbF
Feedback Compensation
The IR3622A is a voltage mode controller; the
control loop is a single voltage feedback path
F ESR =
V OUT
1
2 ? π * ESR * C o
- - - -(15)
including error amplifier and error comparator. To
achieve fast transient response and accurate
output regulation, a compensation circuit is
necessary. The goal of the compensation
network is to provide a closed loop transfer
function with the highest 0dB crossing frequency
and adequate phase margin (greater than 45 o ).
The output LC filter introduces a double pole, –
40dB/decade gain slope above its corner
R 6 Fb
R 5
V REF
Gain(dB)
E/A
Comp
C 9
R 4
Ve
C POLE
resonant frequency, and a total phase lag of 180 o
(see figure 19). The resonant frequency of the LC
filter expressed as follows:
H(s) dB
F Z
F LC =
1
2 ? π L o ? C o
- - - -(14)
Frequency
Fig. 20: TypeII compensation network
Figure 19 shows gain and phase of the LC filter.
Since we already have 180 o phase shift just from
the output filter, the system risks being unstable.
and its asymptotic gain plot
The transfer function (Ve/Vo) is given by:
H ( s ) = ? ? g m *
R 5 ? 1 + sR 4 C 9
R 5 + R 6 ? ?
Gain
0dB
Phase
0
?
?
? *
sC 9
- - - -(16)
-40dB/decade
The (s) indicates that the transfer function varies
as a function of frequency. This configuration
introduces a gain and zero, expressed by:
[ H ( s ) ] = ? g m
? * R 4
-180
F LC Frequency F LC Frequency
Fig. 19: Gain and Phase of LC filter
?
*
R 5 ?
R 5 + R 6 ? ?
- - - -(17)
The IR3622A’s error amplifier is a differential-
input transconductance amplifier. The output is
F z =
1
2 π * R 4 * C 9
- - - -(18)
R 4 =
V osc * F o * F ESR * ( R 5 + R 6 )
available for DC gain control and AC phase
compensation.
The E/A can be compensated either in type II or
type III compensation. When it is used in type II
compensation the transconductance properties of
the E/A become evident and can be used to
cancel one of the output filter poles. This will be
accomplished with a series RC circuit from Comp
pin to ground as shown in figure 20.
This method requires that the output capacitor
has enough ESR to satisfy stability requirements.
In general the output capacitor’s ESR generates
a zero typically at 5kHz to 50kHz which is
essential for an acceptable phase margin. The
ESR zero of the output capacitor expressed as
follows:
www.irf.com
The gain is determined by the voltage divider and
E/A’s transconductance gain.
First select the desired zero-crossover frequency
(Fo):
F o > F ESR and F o ≤ ( 1/5 ~ 1/10 ) * F s
Use the following equation to calculate R 4 :
- - - -(19)
V in * F LC 2 * R 5 * g m
Where:
V in = Maximum Input Voltage
V osc = Oscillator Ramp Voltage
F o = Crossover Frequency
F ESR = Zero Frequency of the Output Capacitor
F LC = Resonant Frequency of the Output Filter
g m = Error Amplifier Transconductance
21
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