参数资料
型号: IR3624MTRPBF
厂商: International Rectifier
英文描述: HIGH FREQUENCY SYNCHRONOUS PWM BUCK CONTROLLER
中文描述: 高频同步PWM降压控制器
文件页数: 15/21页
文件大小: 803K
代理商: IR3624MTRPBF
IR3624MPBF
To cancel one of the LC filter poles, place the
zero before the LC filter resonant frequency pole:
Using equations (15) and (16) to calculate C9.
One more capacitor is sometimes added in
parallel with C4 and R3. This introduces one
more pole which is mainly used to suppress the
switching noise.
The additional pole is given by:
The pole sets to one half of switching frequency
which results in the capacitor C
POLE
:
For a general solution for unconditionally stability
for any type of output capacitors, in a wide range
of ESR values we should implement local
feedback with a compensation network (typeIII).
The typically used compensation network for
voltage-mode controller is shown in figure 15.
In such configuration, the transfer function is
given by:
e
1
V
+
The error amplifier gain is independent of the
transconductance under the following condition:
By replacing Z
in
and Z
f
according to figure 15, the
transformer function can be expressed as:
(16)
-
C
L
2
1
75
.
0
F
F
75
F
o
o
z
LC
z
*
*
%
π
=
=
As known, transconductance amplifier has high
impedance (current source) output, therefore,
consider should be taken when loading the error
amplifier output. It may exceed its source/sink
output current capability, so that the amplifier will
not be able to swing its output voltage over the
necessary range.
The compensation network has three poles and
two zeros and they are expressed as follows:
Cross over frequency is expressed as:
C
C
C
C
R
2
1
F
POLE
4
POLE
4
3
P
+
=
*
*
*
π
2
F
F
For
F
R
*
1
C
1
F
R
1
C
s
P
s
3
4
s
3
POLE
<<
=
*
*
*
π
π
Fig.15: Compensation network with local
feedback and its asymptotic gain plot
IN
m
f
m
o
Z
g
Z
g
1
V
=
15
(
)
[
C
]
)
(
*
+
*
4
C
(
*
)
(
)
(
7
10
3
4
3
4
3
10
8
7
3
3
4
8
C
sR
1
C
C
sR
1
R
R
sC
1
C
sR
1
C
C
sR
1
s
H
+
+
+
+
+
+
=
8
7
10
8
7
2
z
4
3
1
z
3
3
3
4
3
4
3
3
P
7
10
2
P
1
P
R
C
2
1
R
R
C
2
1
F
C
R
2
1
F
C
R
2
1
C
C
C
C
R
2
1
F
C
R
2
1
F
0
F
*
*
)
(
*
*
*
*
*
*
+
*
*
*
π
π
π
π
π
π
+
=
=
=
=
=
o
o
osc
in
7
3
o
C
L
2
1
V
V
C
R
F
*
*
*
*
*
π
=
(17)
-
1
Z
*
g
and
1
Z
*
g
in
m
f
m
>>
>>
V
OUT
V
REF
R
9
R
8
R
10
C
7
C
3
C
4
R
3
Ve
F
Z
1
F
Z
2
F
P
2
F
P
3
E/A
Z
f
Z
IN
Frequency
Gain(dB)
H(s) dB
Fb
Comp
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