参数资料
型号: LTC1909-8EG#TRPBF
厂商: Linear Technology
文件页数: 24/32页
文件大小: 0K
描述: IC REG CTRLR BUCK PWM CM 28-SSOP
标准包装: 2,000
PWM 型: 电流模式
输出数: 1
频率 - 最大: 200kHz
占空比: 90%
电源电压: 4 V ~ 36 V
降压:
升压:
回扫:
反相:
倍增器:
除法器:
Cuk:
隔离:
工作温度: -40°C ~ 85°C
封装/外壳: 28-SSOP(0.209",5.30mm 宽)
包装: 带卷 (TR)
LTC1909-8
APPLICATIO S I FOR ATIO
? = 4 . 7 A
? I L =
? 1 –
( )
I LIMIT ≥
+
4 . 7 A = 18 A
( )( ) . 1 6 ( ) ?
24 V – 1 . 5 V ? 21 . 7 A ?
? ( 1 . 6 ) ( 0 . 012 ? ) = 2 . 12 W
?
2 ?
R ON =
= 330 k
L =
? 1 ?
? = 0 . 8 μ H
( ) ( 1 . 3 ) ( 0 . 012 ? ) +
P BOT =
( )( ) ( )( )( )
sufficient capacitance to prevent the RMS current from
causing additional upstream losses in fuses or batteries.
Other losses, including C OUT ESR loss, Schottky diode D1
conduction loss during dead time and inductor core loss
generally account for less than 2% additional loss. When
making adjustments to improve efficiency, the input cur-
rent is the best indicator of changes in efficiency. If you
make a change and the input current decreases, then the
efficiency has increased. If there is no change in input
current, then there is no change in efficiency.
Checking Transient Response
The regulator loop response can be checked by looking at
the load transient response. Switching regulators take
several cycles to respond to a step in load current. When
a load step occurs, V OUT immediately shifts by an amount
equal to ? I LOAD (ESR), where ESR is the effective series
resistance of C OUT . ? I LOAD also begins to charge or
discharge C OUT generating a feedback error signal used by
the regulator to return V OUT to its steady-state value.
During this recovery time, V OUT can be monitored for
overshoot or ringing that would indicate a stability
problem. The I TH pin external components shown in
Figure 7 will provide adequate compensation for most
applications. For a detailed explanation of switching con-
trol loop theory see Application Note 76.
Design Example
As a design example, take a supply with the following
specifications: V IN = 7V to 24V (15V nominal), V OUT = 1.5V
± 100mV, I OUT(MAX) = 15A, f = 300kHz. First, calculate the
timing resistor with V ON = V OUT :
1
( 300 kHz )( 10 pF )
and choose the inductor for about 40% ripple current at
the maximum V IN :
1 . 5 V ? 1 . 5 V ?
( 300 kHz )( 0 . 4 )( 15 A ) ? 24 V ?
Selecting a standard value of 1 μ H results in a maximum
ripple current of:
1 . 5 V ? 1 . 5 V ?
( 300 kHz ) ( 1 μ H ) ? 24 V ?
Next, choose the synchronous MOSFET switch. Because
of the narrow duty cycle and large current, a single SO-8
MOSFET will have difficulty dissipating the power lost in
the switch. Choosing two IRF7811A (R DS(ON) = 0.013 ? ,
C RSS = 60pF, θ JA = 40 ° C/W) yields a nominal sense voltage
of:
V SNS(NOM) = (15A)(0.5)(1.3)(0.012 ? ) = 117mV
Tying V RNG to INTV CC will set the current sense voltage
range for a nominal value of 140mV with current limit
occurring at 186mV. To check if the current limit is
acceptable, assume a junction temperature of about 100 ° C
above a 50 ° C ambient with ρ 150 ° C = 1.6:
186 mV 1
0 . 5 0 . 012 2
and double check the assumed T J in the MOSFET:
2
P BOT = ?
24 V
T J = 50 ° C + (2.12W)(50 ° C/W) = 156 ° C
Because the top MOSFET is on for such a short time, a
single IRF7811A will be sufficient. Checking its power
dissipation at current limit with ρ 90 ° C = 1.3:
1 .5 V 2
21 . 7 A
24 V
2
1 . 7 24 V 21 . 7 A 60 pF 300 kHz
= 0 . 46 W + 0 . 38 W = 0 . 84 W
T J = 50 ° C + (0.84W)(50 ° C/W) = 92 ° C
The junction temperatures will be significantly less at
nominal current, but this analysis shows that careful
attention to heat sinking will be necessary in this circuit.
C IN is chosen for an RMS current rating of about 6A at
temperature. The output capacitors are chosen for a low
ESR of 0.005 ? to minimize output voltage changes due to
19098f
24
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