参数资料
型号: MAX4254ESD+T
厂商: Maxim Integrated Products
文件页数: 2/16页
文件大小: 0K
描述: IC OPAMP R-R LN QUAD 14-SOIC
标准包装: 2,500
放大器类型: 通用
电路数: 4
输出类型: 推挽式,满摆幅
转换速率: 0.3 V/µs
增益带宽积: 3MHz
电流 - 输入偏压: 1pA
电压 - 输入偏移: 70µV
电流 - 电源: 420µA
电流 - 输出 / 通道: 68mA
电压 - 电源,单路/双路(±): 2.4 V ~ 5.5 V,±1.2 V ~ 2.75 V
工作温度: -40°C ~ 85°C
安装类型: 表面贴装
封装/外壳: 14-SOIC(0.154",3.90mm 宽)
供应商设备封装: 14-SOIC
包装: 带卷 (TR)
UCSP, Single-Supply, Low-Noise,
Low-Distortion, Rail-to-Rail Op Amps
10
Maxim Integrated
MAX4249–MAX4257
Low Distortion
Many factors can affect the noise and distortion that the
device contributes to the input signal. The following
guidelines offer valuable information on the impact of
design choices on Total Harmonic Distortion (THD).
Choosing proper feedback and gain resistor values for
a particular application can be a very important factor
in reducing THD. In general, the smaller the closed-
loop gain, the smaller the THD generated, especially
when driving heavy resistive loads. Large-value feed-
back resistors can significantly improve distortion. The
THD of the part normally increases at approximately
20dB per decade, as a function of frequency.
Operating the device near or above the full-power
bandwidth significantly degrades distortion.
Referencing the load to either supply also improves the
part’s distortion performance, because only one of the
MOSFETs of the push-pull output stage drives the out-
put. Referencing the load to midsupply increases the
part’s distortion for a given load and feedback setting.
(See the Total Harmonic Distortion vs. Frequency graph
in the
Typical Operating Characteristics.)
For gains # 10V/V, the decompensated devices
MAX4249/MAX4255/MAX4256/MAX4257 deliver the
best distortion performance, since they have a higher
slew rate and provide a higher amount of loop gain for
a given closed-loop gain setting. Capacitive loads
below 400pF, do not significantly affect distortion
results. Distortion performance remains relatively con-
stant over supply voltages.
Low Noise
The amplifier’s input-referred, noise-voltage density is
dominated by flicker noise at lower frequencies, and by
thermal noise at higher frequencies. Because the ther-
mal noise contribution is affected by the parallel combi-
nation of the feedback resistive network (RF || RG,
Figure 1), these resistors should be reduced in cases
where the system bandwidth is large and thermal noise
is dominant. This noise contribution factor decreases,
however, with increasing gain settings.
For example, the input noise-voltage density of the cir-
cuit with RF = 100k", RG = 11k" (AV = 10V/V) is en =
15nV/!Hz, en can be reduced to 9nV/!Hz by choosing
RF = 10k", RG = 1.1k" (AV = 10V/V), at the expense
of greater current consumption and potentially higher
distortion. For a gain of 100V/V with RF = 100k", RG =
1.1k", the en is low (9nV/!Hz).
CZ
RF
VOUT
VIN
RG
0
100mV
AV = 2V/V
RF = RG = 10kΩ
VIN =
50mV/div
VOUT =
100mV/div
2
s/div
0
100mV
AV = 2
RF = RG = 100kΩ
CZ = 11pF
50mV/div
100mV/div
VIN
VOUT
2
s/div
Figure 1. Adding Feed-Forward Compensation
Figure 2a. Pulse Response with No Feed-Forward
Compensation
Figure 2b. Pulse Response with 10pF Feed-Forward
Compensation
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