参数资料
型号: SSM2275P
厂商: ANALOG DEVICES INC
元件分类: 音频/视频放大
英文描述: Single Audio Amplifier
中文描述: 1 CHANNEL, AUDIO AMPLIFIER, PDIP8
封装: PLASTIC, DIP-8
文件页数: 12/16页
文件大小: 192K
代理商: SSM2275P
SSM2275/SSM2475
REV. A
–12–
Capacitive Loading
The output of the SSM2275/SSM2475 can tolerate a degree of
capacitive loading. However, under certain conditions, a heavy
capacitive load could create excess phase shift at the output and
put the device into oscillation. The degree of capacitive loading
is dependent on the gain of the amplifier. At unity gain, the am-
plifier could become unstable at loads greater than 600 pF. At
gain greater than unity, the amplifier can handle a higher degree
of capacitive load without oscillating. Figure 35 shows how to
configure the device to prevent oscillations from occurring.
SSM2275
C
L
R
FB
C
FB
R
I
R
B
50k
V
V
IN
INVERTING GAIN AMPLIFIER
V
OUT
SSM2275
C
L
R
FB
C
FB
R
I
R
B
50k
V
V
IN
NONINVERTING GAIN AMPLIFIER
V
OUT
Figure 35. Configurations for Driving Heavy Capacitive
Loads
R
B
should be at least 50 k
. To minimize offset voltage, the
parallel combination of R
FB
and R
I
should be equal to R
B
. Set-
ting a minimum C
F
of 15 pF bandlimits the amplifier enough to
eliminate any oscillation problems from any sized capacitive
load. The low-pass frequency is determined by:
f
R C
dB
F
=
3
1
2
(6)
With R
FB
= 50 k
and C
F
= 15 pF, this results in an amplifier
with a 210 kHz bandwidth that can be used with any capacitive
load. If the amplifier is being used in a noninverting unity gain
configuration and R
I
is omitted, C
FB
should be at least 100 pF.
If the offset voltage can be tolerated at the output, R
FB
can be
replaced by a short and C
FB
can be removed entirely. With the
typical input bias current of 200 nA and R
B
= 50 k
, the in-
crease in offset voltage would be 10 mV. This configuration will
stabilize the amplifier under all capacitive loads.
Single Supply Differential Line Driver
Figure 36 shows a single supply differential line driver circuit
that can drive a 600
load with less than 0.001% distortion.
The design mimics the performance of a fully balanced trans-
former based solution. However, this design occupies much less
board space while maintaining low distortion and can operate
down to dc. Like the transformer based design, either output
can be shorted to ground for unbalanced line driver applications
without changing the circuit gain of 1.
R13 and R14 set up the common-mode output voltage equal to
half of the supply voltage. C1 is used to couple the input signal
and can be omitted if the input’s dc voltage is equal to half of
the supply voltage. The minimum input impedance of the cir-
cuit as seen from V
IN
is:
(
R
R
R
R
R
R
IN
=
+
)
+
(
)
1
5
3
7
11
||
||
(7)
For the values given in Figure 36, R
IN
= 5 k
. With C1 omitted
the circuit will provide a balanced output down to dc, otherwise
the –3 dB corner for the input frequency is set by:
f
R C
dB
L
=
3
1
2
(8)
The circuit can also be configured to provide additional gain if
desired. The gain of the circuit is:
A
V
=
V
OUT
V
IN
=
2(
R
2)
R
1
(9)
where
V
OUT
= V
O1
– V
O2
,
R
1 = R3 = R5 = R7 and,
R
2 = R4 = R6 = R8
Figure 37 shows the THD+N versus frequency response of the
circuit while driving a 600
load at 1 V rms.
SSM2475-A
+12V
R2
10k
V
R1
10k
V
C3
33pF
R9
50
V
R5
10k
V
SSM2475-B
+12V
R8
10k
V
R7
10k
V
C4
33pF
R10
50
V
R3
10k
V
SSM2475-C
+5V
R4
10k
V
C4
10
m
F
R12
10k
V
R11
10k
V
R13
100k
V
C1*
10
m
F
R14
100k
V
C2
10
m
F
+12V
V
IN
V
01
R6
10k
V
C3
10
m
F
V
02
C1* IS OPTIONAL
Figure 36. A Low Noise, Single Supply Differential
Line Driver
FREQUENCY – Hz
0.1
0.01
0.000120
20k
100
T
1k
0.001
10k
V
SY
= 12V
R
L
= 600
V
Figure 37. THD+N vs. Frequency of Differential Line Driver
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