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参数资料
| 型号： | TC170COE |
| 元件分类： | 稳压器 |
| 英文描述： | 0.3 A SWITCHING CONTROLLER, 200 kHz SWITCHING FREQ-MAX, PDSO16 |
| 封装： | SO-16 |
| 文件页数： | 4/9页 |
| 文件大小： | 97K |
| 代理商： | TC170COE |
4
CMOS CURRENT MODE
PWM CONTROLLER
TC170
TC170-5 10/7/99
Peak Current Limit Setup
Resistors R1 and R2 at the current limit input (pin 1) set
the TC170 peak current limit (Figure 1). The potential at pin
1 is easily calculated:
V1 = VREF
R2
R1 + R2
R1 should be selected first. The shutdown circuit fea-
ture is not latched for (VREF – 0.35)/R1 < 50A and is
latched for currents greater than 125
A.
The error amplifier output voltage is clamped from
going above V1 through the limit buffer amplifier. Peak
current is sensed by RS and amplified by the current
amplifier which has a fixed gain of 3.15.
IPCL, the peak current limit, is the current that causes
the PWM comparator noninverting input to exceed V1, the
potential at the inverting input. Once the comparator trip
point is exceeded, both outputs are disabled.
IPCL is easily calculated:
IPCL =
V1 – 0.75V
3.15 (RS)
where:
V1 = VREF
VREF = Internal voltage reference = 5.1V
3.15 = Gain of current-sense amplifier
0.75V = Current limit offset
Both driver outputs (pins 11 and 14) are OFF (LOW)
when the peak current limit is exceeded. When the sensed
current goes below IPCL, the circuit operates normally.
Output Shutdown
The TC170 outputs can be turned OFF quickly through
the shutdown input (pin 16). A signal greater than 350 mV
at pin 16 forces the shutdown comparator output HIGH.
The PWM latch is held set, disabling the outputs.
Q2 is also turned ON. If VREF/R1 is greater than 125A,
positive feedback through the lockup amplifier and Q1
keeps the inverting PWM comparator inverting input below
0.75V. Q3 remains ON even after the shutdown input
signal is removed, because of the positive feedback. The
state can be cleared only through a power-up cycle. Out-
puts will be disabled whenever the potential at pin 1 is
below 0.75V.
The shutdown terminal gives a fast, direct way to dis-
able the TC170 output transistors. System protection and
remote shutdown applications are possible.
R2
R1 + R2
The input pulse to pin 16 should be at least 500nsec
wide and have an amplitude of at least 1V in order to get the
minimum propagation delay from input to output. If these
parameters are met, the delay should be less than
600nsec at 25
°C; however, the delay time will increase as
the device temperature rises.
Soft Restart From Shutdown
A soft restart can be programmed if nonlatched shut-
down operation is used.
A capacitor at pin 1 will cause a gradual increase in
potential toward V1. When the voltage at pin 1 reaches
0.75V, the PWM latch set input is removed and the circuit
establishes a regulated output voltage. The soft-start opera-
tion forces the PWM output drivers to initially operate with
minimum duty cycle and low peak currents.
Even if a soft start is not required, it is necessary to
insert a capacitor between pin 1 and ground if the current IL
is greater than 125
A. This capacitor will prevent "noise
triggering" of the latch, yet minimize the soft-start effect.
Soft-Start Power-Up
During power-up, a capacitor at R1, R2 initiates a soft-
start cycle. As the input voltage (pin 15) exceeds the
undervoltage lockout potential (7.7V), Q4 is turned OFF,
ending undervoltage lockout. Whenever the PWM com-
parator inverting input is below 0.5V, both outputs are
disabled.
When the undervoltage lockout level is passed, the
capacitor begins to charge. The PWM duty cycle increases
until the operating output voltage is reached. Soft-start
operation forces the PWM output drivers to initially operate
with minimum duty cycle and low peak current.
Current-Sense Amplifier
The current-sense amplifier operates at a fixed gain of
3.15. Maximum differential input voltage (VPIN4 – VPIN3) is
1.1V. Common-mode input voltage range is 0V to VIN – 3V.
Resistive-sensing methods are shown in Figure 2. In
Figure 2(A), a simple RC filter limits transient voltage spikes
at pin 4, caused by external output transistor-collector
capacitance. Transformer coupling (Figure 3) offers isola-
tion and better power efficiency, but cost and complexity
increase.
In order to minimize the propagation delay from the input
to the current amplifier to the output terminals, the current
ramp should be in the order of 1
sec in width (min). Typical
time delay values are in the 300 to 400nsec region at 25
°C.
The delay time increases with device temperature so that at
50
°C, the delay times may be increased by as much as
100nsec.
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