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| 型号： | ADE7759ARSZRL |
| 厂商： | Analog Devices Inc |
| 文件页数： | 17/36页 |
| 文件大小： | 0K |
| 描述： | IC ENERGY METERING 1PHASE 20SSOP |
| 标准包装： | 1,500 |
| 输入阻抗： | 390 千欧 |
| 测量误差： | 0.1% |
| 电压 - 高输入/输出： | 2.4V |
| 电压 - 低输入/输出： | 0.8V |
| 电流 - 电源： | 3mA |
| 电源电压： | 4.75 V ~ 5.25 V |
| 测量仪表类型： | 单相 |
| 工作温度： | -40°C ~ 85°C |
| 安装类型： | 表面贴装 |
| 封装/外壳： | 20-SSOP（0.209"，5.30mm 宽） |
| 供应商设备封装： | 20-SSOP |
| 包装： | 带卷 (TR) |
| 配用： | EVAL-ADE7759EBZ-ND - BOARD EVALUATION FOR ADE7759 |
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ADE7759
ALIASING EFFECTS
MAXIMUM
OUTPUT
IMPEDANCE
6k
SAMPLING
LOAD = 10 A
REF IN/OUT
IMAGE
FREQUENCIES
FREQUENCY
PTAT
60 A
1.7k
2.42V
2.5V
12.5k
0
2
447
FREQUENCY – kHz
894
12.5k
Figure 21. ADC and Signal Processing in Channel 1
For a di/dt sensor such as a Rogowski coil, however, the sensor
has 20 dB per decade gain. This will neutralize the –20 dB per
decade attenuation produced by this simple LPF and nullifies
12.5k
12.5k
REFERENCE INPUT
TO ADC CHANNEL 1
(RANGE SELECT)
2.42V, 1.21V, 0.6V
the antialias filter. Therefore, when using a di/dt sensor, mea-
sures should be taken to offset the 20 dB per decade gain coming
from the di/dt sensor and produce sufficient attenuation to
eliminate any aliasing effect. One simple approach is to cascade
two RC filters to produce –40 dB per decade attenuation. The
Figure 22. ADC and Reference Circuit Output
The REF IN/OUT pin can be overdriven by an external source,
e.g., an external 2.5 V reference. Note that the nominal refer-
ence value supplied to the ADCs is now 2.5 V not 2.42 V. This
has the effect of increasing the nominal analog input signal
transfer function for a cascaded filter is the following:
range by 2.5/2.42
100% = 3%, or from 0.5 V to 0.5165 V.
H ( s ) =
1 + sR 1 C 1 + sR 2 C 2 + sR 1 C 2 + s R 1 C 1 R 2 C 2
Code ( ADC ) = 3 . 0492 ×
× 262 , 144
1
2
where R 1 C 1 represents the RC used in the first stage of the
cascade and R 2 C 2 in that of the second stage. The s 2 term in the
transfer function produces a –40 dB/decade attenuation. Note
that to minimize the measurement error, especially at low power
factor, it is important to match the phase angle between the
voltage and the current channel. The small phase mismatch in
the external antialias filter can be corrected using the phase calibra-
tion register (PHCAL[7:0])—see Phase Compensation section .
ADC Transfer Function
Below is an expression which relates the output of the LPF in
the sigma-delta ADC to the analog input signal level. Both ADCs
in the ADE7759 are designed to produce the same output code
for the same input signal level.
V IN
V REF
Therefore, with a full-scale signal on the input of 0.5 V and an
internal reference of 2.42 V, the ADC output code is nominally
165,151 or 2851Fh. The maximum code from the ADC is
± 262,144, which is equivalent to an input signal level of ± 0.794 V.
However, for specified performance it is not recommended that the
full-scale input signal level of 0.5 V be exceeded.
Reference Circuit
Shown in Figure 22 is a simplified version of the reference out-
put circuitry. The nominal reference voltage at the REF IN/OUT
pin is 2.42 V. This is the reference voltage used for the ADCs in
the ADE7759. However, Channel 1 has three input range selec-
tions, which are selected by dividing down the reference value
used for the ADC in Channel 1. The reference value used for
Channel 1 is divided down to 1/2 and 1/4 of the nominal value
by using an internal resistor divider, as shown in Figure 22.
REV. A
The internal voltage reference on the ADE7759 has a tempera-
ture drift associated with it—see ADE7759 Specifications section
for the temperature coefficient specification (in ppm ° C). The
value of the temperature drift varies slightly from part to part.
Since the reference is used for the ADCs in both Channel 1 and 2,
any x% drift in the reference will result in 2x% deviation of the
meter reading. The reference drift resulting from temperature
changes is usually very small, and it is typically much smaller
than the drift of other components on a meter. However, if
guaranteed temperature performance is needed, one needs to
use an external voltage reference. Alternatively, the meter can be
calibrated at multiple temperatures. Real-time compensation
can be achieved easily using the on-chip temperature sensor.
CHANNEL 1 ADC
Figure 23 shows the ADC and signal processing chain for Chan-
nel 1. In waveform sampling mode, the ADC outputs a signed
twos complement 20-bit dataword at a maximum of 27.9 kSPS
(CLKIN/128). The output of the ADC can be scaled by ± 50%
to perform an overall power calibration or to calibrate the ADC
output. While the ADC outputs a 20-bit twos complement
value, the maximum full-scale positive value from the ADC is
limited to 40,000h (+262,144 decimal). The maximum full-
scale negative value is limited to C0000h (–262,144 decimal). If
the analog inputs are overranged, the ADC output code will
clamp at these values. With the specified full-scale analog input
signal of 0.5 V (or 0.25 V or 0.125 V—see Analog Inputs sec-
tion), the ADC will produce an output code that is approximately
63% of its full-scale value. This is illustrated in Figure 23. The
diagram in Figure 23 shows a full-scale voltage signal being
applied to the differential inputs V1P and V1N. The ADC
output swings between D7AE1h (–165,151) and 2851Fh
(+165,151). This is approximately 63% of the full-scale value
40,000h (262,144). Overranging the analog inputs with more
than 0.5 V differential (0.25 V or 0.125 V, depending on
Channel 1 full-scale selection) will cause the ADC output to
increase towards its full-scale value. However, for specified
operation, the differential signal on the analog inputs should
not exceed the recommended value of 0.5 V.
–17 –
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