参数资料
型号: IR3622AMTRPbF
厂商: International Rectifier
英文描述: HIGH FREQUENCY 2-PHASE, SINGLE OR DUAL OUTPUT SYNCHRONOUS STEP DOWN CONTROLLER WITH OUTPUT TRACKING AND SEQUENCING
中文描述: 高频2相,单或双输出同步降压控制器,输出跟踪和排序
文件页数: 14/33页
文件大小: 690K
代理商: IR3622AMTRPBF
IR3622AMPbF
www.irf.com
Feedback Compensation
The IR3622A is a voltage mode controller; the
control loop is a single voltage feedback path
including error amplifier and error comparator. To
achieve fast transient response and accurate
output regulation, a compensation circuit is
necessary. The goal of the compensation
network is to provide a closed loop transfer
function with the highest 0dB crossing frequency
and adequate phase margin (greater than 45o).
The output LC filter introduces a double pole, –
40dB/decade gain slope above its corner
resonant frequency, and a total phase lag of 180o
(see figure 19). The resonant frequency of the LC
filter expressed as follows:
Figure 19 shows gain and phase of the LC filter.
Since we already have 180o phase shift just from
the output filter, the system risks being unstable.
The IR3622A’s error amplifier is a differential-
input transconductance amplifier. The output is
available for DC gain control and AC phase
compensation.
The E/A can be compensated either in type II or
type III compensation. When it is used in type II
compensation the transconductance properties of
the E/A become evident and can be used to
cancel one of the output filter poles. This will be
accomplished with a series RC circuit from Comp
pin to ground as shown in figure 20.
This method requires that the output capacitor
has enough ESR to satisfy stability requirements.
In general the output capacitor’s ESR generates
a zero typically at 5kHz to 50kHz which is
essential for an acceptable phase margin. The
ESR zero of the output capacitor expressed as
follows:
-(14)
-
C
L
2
1
F
o
LC
=
π
Gain
FLC
0dB
Phase
0
FLC
-180
Frequency
-40dB/decade
Fig. 19: Gain and Phase of LC filter
The transfer function (Ve/Vo) is given by:
The (s) indicates that the transfer function varies
as a function of frequency. This configuration
introduces a gain and zero, expressed by:
The gain is determined by the voltage divider and
E/A’s transconductance gain.
First select the desired zero-crossover frequency
(Fo):
Use the following equation to calculate R
4:
Where:
V
in = Maximum Input Voltage
V
osc = Oscillator Ramp Voltage
F
o = Crossover Frequency
F
ESR = Zero Frequency of the Output Capacitor
F
LC = Resonant Frequency of the Output Filter
g
m = Error Amplifier Transconductance
-(15)
-
C
ESR
2
1
F
o
ESR
*
π
=
Ve
VOUT
VREF
R5
R6
R4
C9
E/A
FZ
H(s) dB
Frequency
Gain(dB)
Fb
Comp
CPOLE
Fig. 20: TypeII compensation network
and its asymptotic gain plot
-(16)
-
sC
C
sR
1
R
g
s
H
9
4
6
5
m
+
+
=
*
)
(
()
[]
-(18)
-
C
R
2
1
F
-(17)
-
R
*
R
g
s
H
9
4
z
4
6
5
m
*
π
=
+
=
21
(
)
s
o
ESR
o
F
1/10
~
1/5
F
and
F
*
>
-(19)
-
g
R
F
V
R
F
V
R
m
5
2
LC
in
6
5
ESR
o
osc
4
*
)
(
*
+
=
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