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参数资料
| 型号： | IRU3065CLTR |
| 厂商： | International Rectifier |
| 文件页数： | 4/15页 |
| 文件大小： | 0K |
| 描述： | IC REG CTRLR INV PWM SOT23-6 |
| 标准包装： | 1 |
| PWM 型： | 控制器 |
| 输出数： | 1 |
| 频率 - 最大： | 1.5MHz |
| 占空比： | 100% |
| 电源电压： | 5V |
| 降压： | 无 |
| 升压： | 无 |
| 回扫： | 无 |
| 反相： | 是 |
| 倍增器： | 无 |
| 除法器： | 无 |
| Cuk： | 无 |
| 隔离： | 无 |
| 工作温度： | 0°C ~ 70°C |
| 封装/外壳： | SOT-23-6 |
| 包装： | 剪切带 (CT) |
| 配用： | IRDC3065-ND - LOW PWR SWTCH REG REF DESIGN KIT |
| 其它名称： | *IRU3065CLTR IRU3065CLCT |
IRU3065(PbF)
APPLICATION INFORMATION
Introduction
The IRU3065 is a controller intended for an inverting
regulator solution. For example, to generate –5V from
a 5V supply. The controller is simple and only has a
voltage comparator, current hysteretic comparator, flip-
flop and MOSFET driver. It controls a typical buck boost
converter configured by a P-channel MOSFET, an in-
ductor, a diode and an output capacitor. The sensed
inductor current by a sensing resistor compares with
current comparator. The current comparator uses hys-
teresis to control the turn-on and turn-off of the transis-
tor based upon the inductor current and gated by the
When the output current is below a critical current I OCP ,
the output voltage is regulated at the desired value and
the switching frequency increases as output current
increases. At current I OCP , the switching frequency
reaches its maximum f S(MAX) . In this region, the opera-
tion is in regulation mode. When the current goes above
I OCP , the operation goes into power limit mode. The out-
put voltage starts to decrease and the output power is
limited. The switching frequency is also reduced.
Analysis shows that the current I OCP is determined by:
I OCP = 1 ×
V IN
V IN -V OUT(NOM) +V D
output voltage level. When the inductor current rises
past the hysteresis set point, the output of the current
comparator goes high. The flip-flop is reset and the P-
VI SEN(TH)
2 Rs
×
--(1)
channel MOSFET is turned off. In the mean time, the
current sense reference is reduced to near zero, giving
a zero reference threshold voltage level. As the induc-
tor current passes below this threshold, which indicates
that the inductor ’s stored energy has been transferred
to the output capacitor, the current comparator output
goes high and turns on the output transistor (if the out-
put voltage is low). By means of hysteresis, the induc-
tor charges and discharges and functions as self oscil-
Where:
Rs = Current Sensing Resistance
VI SEN(TH) = Upper Threshold Voltage at the current
comparator (when Vcc=5V, VI SEN(TH) =0.145V)
V IN = Input Voltage
V D = Diode Forward Voltage
V OUT(NOM) = Nominal Output Voltage
The maximum switching frequency is determined by:
lating. The voltage feedback comparator acts as a de-
mand governor to maintain the output voltage at the de-
sired level.
f S(MAX) =
V IN × (V D -V OUT(NOM) )
(V IN +V D -V OUT(NOM ) × L × I PEAK
By hysteresis control, the maximum switch current (also
equals inductor current) is limited by the internal cur-
f S(MAX) =
V IN × (V D -V OUT(NOM) ) × R S
VI SEN(TH) × (V IN +V D -V OUT(NOM) ) × L
---(2)
rent sensing reference. The power limit is automatically
achieved. The switching frequency is determined by a
combination of factors including the inductance, output
load current level and peak inductor current. The theo-
Where:
I PEAK = Peak Inductor Current
I PEAK is determined by:
retical output voltage and switching frequency versus
output current is shown in Figure 3.
I PEAK =
VI SEN(TH)
R S
---(3)
Output
voltage
V out
Regulation
mode
Power limit
mode
I out
The detailed operation can be seen in the theoretical
operation section
f s max
Switching
frequency
f s
I out
I ocp
Figure 3 - Theoretical output voltage and switching
frequency vs. output current.
4
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