参数资料
| 型号： | ISL6308IRZ |
| 厂商： | Intersil |
| 文件页数： | 23/28页 |
| 文件大小： | 0K |
| 描述： | IC CTRLR PWM 3PHASE BUCK 40-QFN |
| 标准包装： | 500 |
| 应用： | 控制器，DDR |
| 输入电压： | 5 V ~ 12 V |
| 输出数： | 1 |
| 输出电压： | 0.6 V ~ 2.3 V |
| 工作温度： | -40°C ~ 85°C |
| 安装类型： | 表面贴装 |
| 封装/外壳： | 40-VFQFN 裸露焊盘 |
| 供应商设备封装： | 40-QFN（6x6） |
| 包装： | 管件 |
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ISL6308
G MOD ( f ) = ------------------------------ ? -----------------------------------------------------------------------------------------------------------
V OSC
1 + s ( f ) ? ( ESR + DCR ) ? C + s ( f ) ? L ? C
d MAX ? V IN ? F LC
G FB ( f ) = ---------------------------------------------------- ?
1 + s ( f ) ? ( R 1 + R 3 ) ? C 3
( 1 + s ( f ) ? R 3 ? C 3 ) ? ? 1 + s ( f ) ? R 2 ? ? --------------------- ? ?
between the closed loop phase at F 0dB and 180°. The
equations that follow relate the compensation network’s poles,
zeros and gain to the components (R 1 , R 2 , R 3 , C 1 , C 2 , and
C 3 ) in Figure 20 and 21. Use the following guidelines for
locating the poles and zeros of the compensation network:
1. Select a value for R 1 (1k Ω to 5k Ω , typically). Calculate
value for R 2 for desired converter bandwidth (F 0 ).
V OSC ? R 1 ? F 0 (EQ. 30)
R 2 = ---------------------------------------------
If setting the output voltage to be equal to the reference
frequency response of the modulator (G MOD ), feedback
compensation (G FB ) and closed-loop response (G CL ):
d MAX ? V IN 1 + s ( f ) ? ESR ? C
2
1 + s ( f ) ? R 2 ? C 1
s ( f ) ? R 1 ? ( C 1 + C 2 ) (EQ. 34)
? -------------------------------------------------------------------------------------------------------------------------
? ? C 1 ? C 2 ? ?
? ? C 1 + C 2 ? ?
set voltage as shown in Figure 21, the design procedure
can be followed as presented. However, when setting the
G CL ( f ) = G MOD ( f ) ? G FB ( f )
where , s ( f ) = 2 π ? f ? j
F Z1 = -------------------------------
output voltage via a resistor divider placed at the input of
the differential amplifier (as shown in Figure 6), in order
to compensate for the attenuation introduced by the
resistor divider, the obtained R 2 value needs be
multiplied by a factor of (R P + R S )/R P . The remainder of
the calculations remain unchanged, as long as the
COMPENSATION BREAK FREQUENCY EQUATIONS
1 (EQ. 35)
2 π ? R 2 ? C 1
F Z2 = -------------------------------------------------
compensated R 2 value is used.
2. Calculate C 1 such that F Z1 is placed at a fraction of the F LC ,
at 0.1 to 0.75 of F LC (to adjust, change the 0.5 factor to
desired number). The higher the quality factor of the output
filter and/or the higher the ratio F CE /F LC , the lower the F Z1
1
2 π ? ( R 1 + R 3 ) ? C 3
(EQ. 36)
C 1 = -----------------------------------------------
F P1 = ---------------------------------------------
C 1 ? C 2
2 π ? R 2 ? ---------------------
2 π ? R 2 ? C 1 ? F CE – 1
F P2 = -------------------------------
frequency (to maximize phase boost at F LC ).
1
2 π ? R 2 ? 0.5 ? F LC
3. Calculate C 2 such that F P1 is placed at F CE .
C 1
C 2 = --------------------------------------------------------
(EQ. 31)
(EQ. 32)
1
C 1 + C 2
1
2 π ? R 3 ? C 3
Figure 22 shows an asymptotic plot of the DC/DC
(EQ. 37)
(EQ. 38)
R 3 = ----------------------
F SW
F LC
C 3 = -------------------------------------------------
4. Calculate R 3 such that F Z2 is placed at F LC . Calculate C 3
such that F P2 is placed below F SW (typically, 0.5 to 1.0
times F SW ). F SW represents the per-channel switching
frequency. Change the numerical factor to reflect desired
placement of this pole. Placement of F P2 lower in
frequency helps reduce the gain of the compensation
network at high frequency, in turn reducing the HF ripple
component at the COMP pin and minimizing resultant
duty cycle jitter.
R 1
------------ – 1
(EQ. 33)
1
2 π ? R 3 ? 0.7 ? F SW
It is recommended a mathematical model is used to plot the
loop response. Check the loop gain against the error
amplifier ’s open-loop gain. Verify phase margin results and
adjust as necessary. The following equations describe the
23
converter ’s gain vs frequency. The actual Modulator Gain
has a high gain peak dependent on the quality factor (Q) of
the output filter, which is not shown. Using the above
guidelines should yield a compensation gain similar to the
curve plotted. The open loop error amplifier gain bounds the
compensation gain. Check the compensation gain at F P2
against the capabilities of the error amplifier. The closed loop
gain, G CL , is constructed on the log-log graph of Figure 22
by adding the modulator gain, G MOD (in dB), to the feedback
compensation gain, G FB (in dB). This is equivalent to
multiplying the modulator transfer function and the
compensation transfer function and then plotting the
resulting gain.
A stable control loop has a gain crossing with close to a
-20dB/decade slope and a phase margin greater than 45
degrees. Include worst case component variations when
determining phase margin. The mathematical model
presented makes a number of approximations and is
generally not accurate at frequencies approaching or
exceeding half the switching frequency. When designing
compensation networks, select target crossover frequencies
in the range of 10% to 30% of the per-channel switching
frequency, F SW .
FN9208.4
September 30, 2008
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| ISL6308IRZ-T | 功能描述:电压模式 PWM 控制器 DAC-LESS MULTI-PHS PWM CNTRLR W/3-DRVRS RoHS:否 制造商:Texas Instruments 输出端数量:1 拓扑结构:Buck 输出电压:34 V 输出电流: 开关频率: 工作电源电压:4.5 V to 5.5 V 电源电流:600 uA 最大工作温度:+ 125 C 最小工作温度:- 40 C 封装 / 箱体:WSON-8 封装:Reel |
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