参数资料
型号: LT3574IMS#TRPBF
厂商: Linear Technology
文件页数: 15/24页
文件大小: 0K
描述: IC REG FLYBK ISO ADJ .65A 16MSOP
标准包装: 2,500
类型: 回扫,隔离
输出类型: 可调式
输出数: 1
输出电压: 可调至 60V
输入电压: 3 V ~ 40 V
PWM 型: 电流模式,混合
频率 - 开关: 40kHz ~ 1MHz
电流 - 输出: 650mA
同步整流器:
工作温度: -40°C ~ 125°C
安装类型: 表面贴装
封装/外壳: 16-TFSOP(0.118",3.00mm 宽)
包装: 带卷 (TR)
供应商设备封装: 16-MSOP
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LT3574
APPLICATIONS INFORMATION
N P
50 ? V IN ( MAX )
+ V
I OUT ( MAX ) = 0 . 8 ? ( 1 ? D ) ?
NI PK
D =
OverdrivingtheBIASPinwithaThirdWinding
The LT3574 provides excellent output voltage regulation
without the need for an opto-coupler, or third winding, but
for some applications with higher input voltages (>20V),
it may be desirable to add an additional winding (often
called a third winding) to improve the system efficiency.
For proper operation of the LT3574, if a winding is used as
a supply for the BIAS pin, ensure that the BIAS pin voltage
is at least 3.15V and always less than the input voltage.
For a typical 24V IN application, overdriving the BIAS pin
will improve the efficiency gain 4% to 5%.
Loop Compensation
The LT3574 is compensated using an external resistor-
capacitor network on the VC pin. Typical values are in the
range of R C = 50k and C C = 1nF (see the numerous sche-
matics in the Typical Applications section for other possible
values). If too large of an R C value is used, the part will be
more susceptible to high frequency noise and jitter. If too
small of an R C value is used, the transient performance will
suffer. The value choice for C C is somewhat the inverse
of the R C choice: if too small a C C value is used, the loop
may be unstable, and if too large a C C value is used, the
transient performance will also suffer. Transient response
plays an important role for any DC/DC converter.
Design Example
The following example illustrates the converter design
process using LT3574.
Given the input voltage of 20V to 28V, the required output
is 5V, 0.5A.
1. Select the transformer turns ratio to accommodate
the output.
The output voltage is reflected to the primary side by a
factor of turns ratio N. The switch voltage stress V SW is
expressed as:
N =
N S
V SW ( MAX ) = V IN + N ( V OUT + V F ) < 50 V
or rearranged to:
N <
( V OUT F )
On the other hand, the primary-side current is multiplied by
the same factor of N. The converter output capability is:
1
2
N ( V OUT + V F )
V IN + N ( V OUT + V F )
The transformer turns ratio is selected such that the con-
verter has adequate current capability and a switch stress
below 50V. Table 6 shows the switch voltage stress and
output current capability at different transformer turns
ratio.
Table 6. Switch Voltage Stress and Output Current Capability vs
Turns Ratio
V SW(MAX) AT V IN(MAX) I OUT(MAX) AT V IN(MIN) DUTY CYCLE
N (V) (A) (%)
V IN(MIN) = 20V, V IN(MAX) = 28V, V OUT = 5V, V F = 0.5V
and I OUT = 0.5A
1:1
2:1
3:1
4:1
33.5
39
44.5
50
0.34
0.57
0.73
0.84
16~22
28~35
37~45
44~52
3574f
  
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