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参数资料
| 型号： | TPS40061PWPG4 |
| 厂商： | TEXAS INSTRUMENTS INC |
| 元件分类： | 稳压器 |
| 英文描述： | SWITCHING CONTROLLER, 1000 kHz SWITCHING FREQ-MAX, PDSO16 |
| 封装： | GREEN, PLASTIC, HTSOOP-16 |
| 文件页数： | 5/33页 |
| 文件大小： | 750K |
| 代理商： | TPS40061PWPG4 |
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C
BPN10 +
Qg
DV
(F)
(8)
C
BP10V +
Q
gSR
DV
(F)
(9)
SYNCHRONIZING TO AN EXTERNAL SUPPLY
R
T(dummy) +
1
f
SYNC
17.82
10*6
* 23 kW
(10)
R
KFF + VIN(min) * 3.5 V
65.27
R
T(dummy) ) 1502
kW
(11)
SELECTING THE INDUCTOR VALUE
L +
V
IN * VO
V
O
V
IN
DI
f
SW
(H)
(12)
SLUS543E – DECEMBER 2002 – REVISED JUNE 2006
APPLICATION INFORMATION (continued)
The 10-V reference pin, BP10V needs to provide energy for the synchronous MOSFET gate drive via the BP10V
capacitor. Neglecting any efficiency penalty, the BP10V capacitance is described in Equation 9.
The TPS4006x can be synchronized to an external clock through the SYNC pin. The SW node rises on the
falling edge of the SYNC signal. The synchronization frequency should be in the range of 20% to 30% higher
than its programmed free-run frequency. The clock frequency at the SYNC pin replaces the master clock
generated by the oscillator circuit. Pulling the SYNC pin low programs the TPS4006x to freely run at the
frequency programmed by RT.
Internally, the SYNC pin has a pull-down current between 5 A and 10 A. In order to synchronize the device to
an external clock signal, the SYNC pin has to be overdriven from the external clock circuit. Normal logic gates or
an external MOSFET with a pull-up resistor of 10 k
is adequate.
Internally there is a delay of between approximately 50 ns and 100 ns from the time the SYNC pin is pulled low
and the HDRV signal goes high to turn on the upper MOSFET. Additionally, there is some delay as the
MOSFET gate charges to turn on the upper MOSFET, typically between 20 ns and 50 ns.
The higher synchronization must be factored in when programming the PWM ramp generator circuit. If the PWM
ramp is interrupted by the SYNC pulse, a UVLO condition is declared and the PWM becomes disabled. Typically
this is of concern under low-line conditions only. In any case, RKFF needs to be adjusted for the higher switching
frequency. In order to specify the correct value for RKFF at the synchronizing frequency, calculate a 'dummy'
value for RT that would cause the oscillator to run at the synchronizing frequency. Do not use this value of RT in
the design.
Use the value of RT(dummy) to calculate the value for RKFF.
where:
R
T is in k
This value of RKFF ensures that UVLO is not engaged when operating at the synchronization frequency.
The inductor value determines the magnitude of ripple current in the output capacitors as well as the load
current at which the converter enters discontinuous mode. Too large an inductance results in lower ripple current
but is physically larger for the same load current. Too small an inductance results in larger ripple currents and a
greater number of (or more expensive output capacitors for) the same output ripple voltage requirement. A good
compromise is to select the inductance value such that the converter doesn't enter discontinuous mode until the
load approximated somewhere between 10% and 30% of the rated output. The inductance value is described in
where:
V
O is the output voltage
I is the peak-to-peak inductor current
13
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