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参数资料
| 型号： | MAX17582GTM+T |
| 厂商： | Maxim Integrated Products |
| 文件页数： | 21/42页 |
| 文件大小： | 0K |
| 描述： | IC CTLR PWM 2PH IMVP-6.5 48-TQFN |
| 产品培训模块： | Lead (SnPb) Finish for COTS Obsolescence Mitigation Program |
| 标准包装： | 2,500 |
| 系列： | Quick-PWM™ |
| 应用： | 控制器，Intel IMVP-6.5? |
| 输入电压： | 4.5 V ~ 5.5 V |
| 输出数： | 1 |
| 输出电压： | 0.01 V ~ 1.5 V |
| 工作温度： | -40°C ~ 105°C |
| 安装类型： | 表面贴装 |
| 封装/外壳： | 48-WFQFN 裸露焊盘 |
| 供应商设备封装： | 48-TQFN-EP（6x6） |
| 包装： | 带卷 (TR) |
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Dual-Phase, Quick-PWM Controller for
IMVP-6.5 CPU Core Power Supplies
CCI and FB. The resulting compensation current and
voltage are determined by the following equations:
I CCI = G m (V CSP1 - V CSN1 ) - G m (V CSP2 - V CSN2 )
V CCI = V FB + I CCI Z CCI
causes LX_ to go high earlier than normal, extending
the on-time by a period equal to the DH_-rising dead
time. For loads above the critical conduction point,
where the dead-time effect is no longer a factor, the
actual switching frequency (per phase) is:
where Z CCI is the impedance at the CCI output. The
secondary on-time one-shot uses this integrated signal
(V CCI ) to set the secondary high-side MOSFETs on-
time. When the main and secondary current-sense sig-
f SW =
( V OUT + V DROP 1 )
t ON ( V IN + V DROP 1 - V DROP 2 )
t ON ( SEC ) = T SW ? CCI
= T SW ? FB
? ? + T SW ? ?
R CS = ?
? R 2 ?
? R 1 + R 2 ? ? DCR
nals (V CM = V CSP1 - V CSN1 and V CS = V CSP2 - V CSN2 )
become unbalanced, the transconductance amplifiers
adjust the secondary on-time, which increases or
decreases the secondary inductor current until the cur-
rent-sense signals are properly balanced:
? V + 0.075 V ?
?
? V IN ?
? V + 0.0775V ? ? I CCI Z CCI ?
?
? V IN V IN ?
= ( Main On-ttime ) + ( Secondary Current Balance Correctio n )
This algorithm results in a nearly constant switching fre-
quency and balanced inductor currents despite the
lack of a fixed-frequency clock generator. The benefits
of a constant switching frequency are twofold: first, the
frequency can be selected to avoid noise-sensitive
regions such as the 455kHz IF band; second, the
inductor ripple-current operating point remains relative-
ly constant, resulting in easy design methodology and
predictable output-voltage ripple. The on-time one-
shots have good accuracy at the operating points
specified in the Electrical Characteristics table. On-
times at operating points far removed from the condi-
tions specified in the Electrical Characteristics table
can vary over a wider range.
On-times translate only roughly to switching frequen-
cies. The on-times guaranteed in the Electrical
Characteristics table are influenced by switching
delays in the external high-side MOSFET. Resistive
losses, including the inductor, both MOSFETs, output
capacitor ESR, and PCB copper losses in the output
where V DROP1 is the sum of the parasitic voltage drops in
the inductor discharge path, including synchronous recti-
fier, inductor, and PCB resistances; V DROP2 is the sum of
the parasitic voltage drops in the inductor charge path,
including high-side switch, inductor, and PCB resis-
tances; and t ON is the on-time as determined above.
Current Sense
The output current of each phase is sensed. Low-offset
amplifiers are used for current balance, voltage-posi-
tioning gain, and current limit. Sensing the current at
the output of each phase offers advantages, including
less noise sensitivity, more accurate current sharing
between phases, and the flexibility of using either a cur-
rent-sense resistor or the DC resistance of the output
inductor.
Using the DC resistance (R DCR ) of the output inductor
allows higher efficiency. In this configuration, the initial
tolerance and temperature coefficient of the inductor’s
DCR must be accounted for in the output-voltage
droop-error budget and power monitor. This current-
sense method uses an RC filtering network to extract
the current information from the output inductor (see
Figure 3). The resistive divider used should provide a
current-sense resistance (R CS ) low enough to meet the
current-limit requirements, and the time constant of the
RC network should match the inductor’s time constant
(L/R CS ):
R
and:
? ? R 1 + R 2 ? ?
and ground tend to raise the switching frequency at
higher output currents. Also, the dead-time effect
increases the effective on-time, reducing the switching
frequency. It occurs only during forced-PWM operation
R CS =
L ? 1 1 ?
C EQ
and dynamic output-voltage transitions when the induc-
tor current reverses at light- or negative-load currents.
With reversed inductor current, the inductor ’s EMF
where R CS is the required current-sense resistance and
R DCR is the inductor’s series DC resistance.
______________________________________________________________________________________
21
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