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| 型号： | LTC4110EUHF#TRPBF |
| 厂商： | Linear Technology |
| 文件页数： | 36/52页 |
| 文件大小： | 0K |
| 描述： | IC BATTERY BACKUP MANAGER 38-QFN |
| 标准包装： | 2,500 |
| 功能： | 备份管理 |
| 电池化学： | 铅酸，锂离子，锂聚合物，镍镉，镍氢，超级电容器 |
| 电源电压： | 4.5 V ~ 19 V |
| 工作温度： | -40°C ~ 85°C |
| 安装类型： | 表面贴装 |
| 封装/外壳： | 38-WFQFN 裸露焊盘 |
| 供应商设备封装： | 38-QFN（5x7） |
| 包装： | 带卷 (TR) |
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LTC4110
APPLICATIONS INFORMATION
to monitor the primary current in both sides with a single
R SNS(FET) resistor, both transformer windings must be
connected prior to R SNS(FET) . Since the secondary phase
is always 180 degrees out of phase with the primary, the
following current waveform in Figure 14 is the result.
I PRI
in calibration mode input current is regulated, not the
output current.
The LTC4110’s I SENSE pin has a limited usable positive
voltage range for V SNS(FET) . The range must be between
30mV and 150mV peak in both charge and calibration
modes when operating at full current. The negative portion
0
I PRI
N
PRIMARY CURRENT
SECONDARY CURRENT
4110 F14
of the waveform is also monitored but has a dynamic trip
level that tracks the actual primary current. The trip level
has a gain factor of –3. If the secondary current trips the
negative level, the ?yback goes into current limit.
Figure 14. R SNS(FET) Current Waveform
In terms of current sensing, the primary current portion
of the above waveform is monitored for peak current (DC
+ AC) at any time in any mode. It does not monitor the
batteries’ DC current. The LTC4110 uses leading edge
blanking to mask out noise to make the application of this
part simple to use. The secondary portion of the above
waveform is monitored for negative peak current to sense
for short circuit.
The value of ripple current, Δ I, is a direct function of the
transformer inductance. See transformer section for more
information about transformer ripple current.
You must calculate the I PRI for both charge current mode
and calibration current mode. The equation for calculating
These limits have the following implications:
? The ratio of peak current between I PRI(CHG) and I PRI(CAL)
cannot be greater than 5-to-1 as seen by R SNS(FET) .
? The transformer turns ratio will approximately reduce
the maximum available DC current ratio between I CHG
to I CAL by a factor of 1/N. The additional variables
being ripple current and ef?ciency.
? You cannot use a transformer with a turns ratio
greater than 3.
? Because ef?ciency is always less than 100%, you
never have to worry about peak secondary current
causing a false short circuit trip within the turns ratio
limit of 3 or less.
As a design starting point, use the lowest value between
I PRI(CHG) =
I CHG V BAT
the I PRI for charge mode is as follows:
? + N +
E V DCIN
V BAT ? V DCIN
2 ? f ? L PRI ? ( V BAT + N ? V DCIN )
I PRI for the Calibration mode is as follows:
(1)
I PRI(CHG) and I PRI(CAL) for I PRI , let V SNS(FET) be set to 50mV
for good ef?ciency and solve for R SNS(FET) .
V SNS(FET )
R SNS ( FET ) =
I PRI
With an initial value of R SNS(FET) identi?ed, solve for
V SNS(FET) using the highest value between I PRI(CHG) or
I PRI(CAL) and see if the calculated value of V SNS(FET) falls
I PRI(CAL) = I CAL ?
V BAT
N ? V DCIN
+ 1 +
below the upper limits. If it is too high, you may have to
drop the value of R SNS(FET). If you cannot meet the V SNS(FET)
upper or lower limits and/or ratio limits, you may have to
V BAT ? V DCIN
2 ? f ? (N 2 ? L PRI ) ? V DCIN +
V BAT
N
(2)
back off on one of the I CHG and I CAL DC current parameters
to compensate.
Once within all the limits, optimize R SNS(FET) for maximum
The value of E is the ?yback ef?ciency. Use 80% (0.8) as
the value since the ?yback uses synchronous recti?ca-
tion. E is not used for the calibration equation because
ef?ciency by using very low value of R SNS(FET) and/or ?nd
a popular R SNS(FET) value. The tradeoff of using lower
values of R SNS(FET) is increased waveform jitter due to
higher switching noise sensitivity issues.
4110fb
36
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