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参数资料
| 型号： | MAX17030EVKIT+ |
| 厂商： | Maxim Integrated Products |
| 文件页数： | 21/39页 |
| 文件大小： | 0K |
| 描述： | EVALUATION KIT FOR MAX17030 |
| 产品培训模块： | Lead (SnPb) Finish for COTS Obsolescence Mitigation Program |
| 标准包装： | 1 |
| 系列： | Quick-PWM™ |
| 主要目的： | DC/DC，步降 |
| 输出及类型： | 1，非隔离 |
| 输出电压： | 0 ~ 1.5 V |
| 输入电压： | 7 ~ 26 V |
| 稳压器拓扑结构： | 降压 |
| 板类型： | 完全填充 |
| 已供物品： | 板 |
| 已用 IC / 零件： | MAX17030 |
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1/2/3-Phase Quick-PWM
IMVP-6.5 VID Controllers
t ON ( SEC ) = T SW ? CCI
= T SW ? FB
? ? + T SW ? ?
R CS = ?
? R 2 ?
? R 1 + R 2 ? ? DCR
When the main and other phase current-sense signals
(V CM = V CMP - V CMN and V CS = V CSP - V CSM ) become
unbalanced, the transconductance amplifiers adjust the
other phase’s on-time, which increases or decreases
the phase inductor current until the current-sense sig-
nals are properly balanced:
? V + 0.075 V ?
?
? V IN ?
? V + 0 . 0775V ? ? I CCI Z CCI ?
?
? V IN V IN ?
= ( Main On-ttime ) + ( Secondary Current Balance Correctio n )
where V CCI is the internal integrator node for each
slave ’s current-balance integrator, and Z CCI is the
effective impedance at that node.
During phase overlap, t ON is calculated based on
phase 1’s on-time requirements, but reduced by 33%
when operating with three phases.
For a 3-phase regulator, each phase cannot be
enabled until the other 2 phases have completed their
on-time and the minimum off-times have expired. As
such, the minimum period is limited by 3 x (t ON +
t OFF(MIN) ). Maximum t ON is dependent on minimum V IN
including MOSFET, inductor, and PCB resistances;
V CHG is the sum of the parasitic voltage drops in the
inductor charge path, including high-side switch,
inductor, and PCB resistances; and t ON is the on-time
as determined above.
Current Sense
The MAX17030/MAX17036 sense the output current of
each phase allowing the use of current-sense resistors
on inductor DCR as the current-sense element. Low-
offset amplifiers are used for current balance, voltage-
positioning gain, and current limit.
Using the DC resistance (R DCR ) of the output inductor
allows higher efficiency. The initial tolerance and tem-
perature coefficient of the inductor ’s DCR must be
accounted for in the output-voltage droop-error budget
and current monitor. This current-sense method uses
an RC filtering network to extract the current information
from the output inductor (see Figure 4). The RC network
should match the inductor’s time constant (L/R DCR ):
R
and:
+
and maximum output voltage:
T SW(MIN) = N PH x (t ON(MAX) + t OFF(MIN) )
where:
R CS =
L ? 1 1 ?
C EQ ? ? R 1 R 2 ? ?
so:
t ON(MAX) = V FB(MAX) /V IN(MIN x T SW(MIN)
where R CS is the required current-sense resistance,
and R DCR is the inductor’s series DC resistance. Use
the typical inductance and R DCR values provided by
( V OUT + V DIS )
t ON IN DIS CHG )
( V + V
f SW =
= C EQ R EQ
T SW(MIN) = t OFF(MIN) /[1/N PH – V IN(MAX) /V IN(MIN) ]
Hence, for a 7V input and 1.1V output, 500kHz is the
maximum switching frequency. Running at this limit is
not desirable as there is no room to allow the regulator
to make adjustments without triggering phase overlap.
For a 3-phase, high-current application with minimum
8V input, the practical switching frequency is 300kHz.
On-times translate only roughly to switching frequen-
cies. The on-times guaranteed in the Electrical
Characteristics are influenced by parasitics in the con-
duction paths and propagation delays. For loads above
the critical conduction point, where the dead-time effect
(LX flying high and conducting through the high-side
FET body diode) is no longer a factor, the actual
switching frequency (per phase) is:
? V
where V DIS and V CHG are the sum of the parasitic volt-
age drops in the inductor discharge and charge paths,
the inductor manufacturer. To minimize the current-
sense error due to the current-sense inputs’ bias current
(I CSP_ and I CSN_ ), choose R1//R2 to be less than 2k Ω
and use the above equation to determine the sense
capacitance (C EQ ). Choose capacitors with 5% toler-
ance and resistors with 1% tolerance specifications.
Temperature compensation is recommended for this
current-sense method. See the Voltage Positioning and
Loop Compensation section for detailed information.
When using a current-sense resistor for accurate out-
put-voltage positioning, the circuit requires a differential
RC filter to eliminate the AC voltage step caused by the
equivalent series inductance (L ESL ) of the current-
sense resistor (see Figure 4). The ESL induced voltage
step might affect the average current-sense voltage.
The RC filter’s time constant should match the L ESL /
R SENSE time constant formed by the current-sense
resistor’s parasitic inductance:
L ESL
R SENSE
______________________________________________________________________________________
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相关代理商/技术参数 |
参数描述 |
|---|---|
| MAX17030EVKIT+ | 功能描述:电源管理IC开发工具 MAX17030 Eval Kit RoHS:否 制造商:Maxim Integrated 产品:Evaluation Kits 类型:Battery Management 工具用于评估:MAX17710GB 输入电压: 输出电压:1.8 V |
| MAX17030GTL+ | 功能描述:电压模式 PWM 控制器 1/2/3-Phase PWM IMVP-6.5 VID Ctlr RoHS:否 制造商:Texas Instruments 输出端数量:1 拓扑结构:Buck 输出电压:34 V 输出电流: 开关频率: 工作电源电压:4.5 V to 5.5 V 电源电流:600 uA 最大工作温度:+ 125 C 最小工作温度:- 40 C 封装 / 箱体:WSON-8 封装:Reel |
| MAX17030GTL+T | 功能描述:电压模式 PWM 控制器 1/2/3-Phase PWM IMVP-6.5 VID Ctlr RoHS:否 制造商:Texas Instruments 输出端数量:1 拓扑结构:Buck 输出电压:34 V 输出电流: 开关频率: 工作电源电压:4.5 V to 5.5 V 电源电流:600 uA 最大工作温度:+ 125 C 最小工作温度:- 40 C 封装 / 箱体:WSON-8 封装:Reel |
| MAX17031ETG+ | 功能描述:电压模式 PWM 控制器 Dual PWM Step-Down Controller RoHS:否 制造商:Texas Instruments 输出端数量:1 拓扑结构:Buck 输出电压:34 V 输出电流: 开关频率: 工作电源电压:4.5 V to 5.5 V 电源电流:600 uA 最大工作温度:+ 125 C 最小工作温度:- 40 C 封装 / 箱体:WSON-8 封装:Reel |
| MAX17031ETG+T | 功能描述:电压模式 PWM 控制器 Dual PWM Step-Down Controller RoHS:否 制造商:Texas Instruments 输出端数量:1 拓扑结构:Buck 输出电压:34 V 输出电流: 开关频率: 工作电源电压:4.5 V to 5.5 V 电源电流:600 uA 最大工作温度:+ 125 C 最小工作温度:- 40 C 封装 / 箱体:WSON-8 封装:Reel |
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