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参数资料
| 型号： | MAX8792ETD+T |
| 厂商： | Maxim Integrated Products |
| 文件页数： | 22/28页 |
| 文件大小： | 0K |
| 描述： | IC PWM CTRLR STEP-DWN 14TDFN |
| 产品培训模块： | Lead (SnPb) Finish for COTS Obsolescence Mitigation Program |
| 标准包装： | 1 |
| 应用： | PWM 控制器 |
| 输入电压： | 2 V ~ 26 V |
| 电源电压： | 4.5 V ~ 5.5 V |
| 电流 - 电源： | 700µA |
| 工作温度： | -40°C ~ 85°C |
| 安装类型： | 表面贴装 |
| 封装/外壳： | 14-WFDFN 裸露焊盘 |
| 供应商设备封装： | 14-TDFN-EP（3x3） |
| 包装： | 标准包装 |
| 其它名称： | MAX8792ETD+TDKR |
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Single Quick-PWM Step-Down
Controller with Dynamic REFIN
With most chemistries (polymer, tantalum, aluminum
electrolytic), the actual capacitance value required
relates to the physical size needed to achieve low ESR
and the chemistry limits of the selected capacitor tech-
nology. Ceramic capacitors provide low ESR, but the
capacitance and voltage rating (after derating) are
determined by the capacity needed to prevent V SAG
and V SOAR from causing problems during load tran-
sients. Generally, once enough capacitance is added
to meet the overshoot requirement, undershoot at the
rising load edge is no longer a problem (see the V SAG
and V SOAR equations in the Transient Response sec-
tion). Thus, the output capacitor selection requires
carefully balancing capacitor chemistry limitations
For a standard 300kHz application, the effective zero
frequency must be well below 95kHz, preferably below
50kHz. With these frequency requirements, standard
tantalum and polymer capacitors already commonly
used have typical ESR zero frequencies below 50kHz,
allowing the stability requirements to be achieved with-
out any additional current-sense compensation. In the
standard application circuit (Figure 1), the ESR needed
to support a 15mV P-P ripple is 15mV/(10A x 0.3) =
5m Ω . Two 330μF, 9m Ω polymer capacitors in parallel
provide 4.5m Ω (max) ESR and 1/(2 π x 330μF x 9m Ω ) =
53kHz ESR zero frequency.
(capacitance vs. ESR vs. voltage rating) and cost.
Output Capacitor Stability Considerations
TON
BST
C IN
INPUT
For Quick-PWM controllers, stability is determined by
the in-phase feedback ripple relative to the switching
frequency, which is typically dominated by the output
DH
L1
PWR
ESR. The boundary of instability is given by the following
LX
OUTPUT
≥
equation:
f SW 1
π 2 π R EFF C OUT
R EFF = R ESR + R PCB + R COMP
MAX8792
DL
FB
PWR
C OUT
PWR
R ESR C OUT ≥
where C OUT is the total output capacitance, R ESR is the
total equivalent-series resistance of the output capaci-
tors, R PCB is the parasitic board resistance between
AGND
GND
PWR
STABILITY REQUIREMENT
1
2f SW
the output capacitors and feedback sense point, and
R COMP is the effective resistance of the DC- or AC-cou-
pled current-sense compensation (see Figure 10).
Figure 8. Standard Application with Output Polymer or Tantalum
TON
BST
C IN
INPUT
PCB PARASITIC RESISTANCE
SENSE RESISTANCE FOR EVALUATION
PWR
DH
L1
LX
OUTPUT
DL
C OUT
PWR
C LOAD
PWR
MAX8792
FB
PWR
R COMP
100 Ω
OUTPUT VOLTAGE REMOTELY
SENSED NEAR POINT OF LOAD
GND
AGND
PWR
STABILITY REQUIREMENT
R ESR C OUT ≥
1
2f SW
AND R COMP C COMP ≥
1
f SW
FEEDBACK RIPPLE IN PHASE WITH INDUCTOR CURRENT
Figure 9. Remote-Sense Compensation for Stability and Noise Immunity
22
______________________________________________________________________________________
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